MultiLevel PreCorrelation RFI Flagging for RealTime Implementation on UniBoard
Abstract
Because of the denser active use of the spectrum, and because of radio telescopes higher sensitivity, radio frequency interference (RFI) mitigation has become a sensitive topic for current and future radio telescope designs. Even if quite sophisticated approaches have been proposed in the recent years, the majority of RFI mitigation operational procedures are based on postcorrelation corrupted data flagging. Moreover, given the huge amount of data delivered by current and next generation radio telescopes, all these RFI detection procedures have to be at least automatic and, if possible, realtime.
In this paper, the implementation of a realtime precorrelation RFI detection and flagging procedure into generic highperformance computing platforms based on Field Programmable Gate Arrays (FPGA) is described, simulated and tested. One of these boards, UniBoard, developed under a Joint Research Activity in the RadioNet FP7 European programme is based on eight FPGAs interconnected by a high speed transceiver mesh. It provides up to 4 TMACs with ®Altera Stratix IV FPGA and 160 Gbps data rate for the input data stream.
The proposed concept is to continuously monitor the data quality at different stages in the digital preprocessing pipeline between the antennas and the correlator, at station level and core level. In this way, the detectors are applied at stages where different timefrequency resolutions can be achieved and where the interferencetonoise ratio is maximum, right before any dilution of RFI characteristics by subsequent channelizations or signal recombinations. The detection decisions could be linked to a RFI statistics database or could be attached to the data for later stage flagging.
Considering the high inout data rate in the precorrelation stages, only realtime and gothrough detectors (i.e. no iterative processing) can be implemented. In this paper, a realtime and adaptive detection scheme is described.
An ongoing case study has been set up with the Electronic MultiBeam Radio Astronomy Concept (EMBRACE) radio telescope facility at Nançay Observatory. The objective is to evaluate the performances of this concept in term of hardware complexity, detection efficiency and additional RFI metadata rate cost. The UniBoard implementation scheme is described.
Grotunits=360
Corresponding author.
Received (to be inserted by publisher); Revised (to be inserted by publisher); Accepted (to be inserted by publisher);
Keywords: RFI mitigation, precorrelation techniques, flagging, hardware implementation, FPGA, UniBoard
1 Introduction
The sensitivity of stateoftheart telescopes is over ten orders of magnitude higher than in most communications systems. Although radio telescopes are best located in relatively remote areas, astronomical observations may still be hampered by manmade radio frequency interference (RFI). Under this assumption, one basic or recurrent scenario could be to carefully design the analogue parts and to limit the fulltime digital measures to flagging.
In particular, it would be worthwhile to continuously monitor the quality of the data. Given the extreme sensitivity of current and future radio telescopes, this task has to be a by product of the instrument itself. It would therefore be interesting to implement some detection methods as regular signal processing tasks at station or core levels. The detection results could be linked to a kind of RFI statistics database or attached to the data for flagging.
An exhaustive survey on RFI mitigation for radio astronomy (Boonstra & weber, 2009) and a workshop (PoS, 2010) dedicated to that topic have shown various developments for preserving radio astronomical observations.
Currently, in routine practice, the majority of RFI mitigation procedures are based on corrupted data detection and flagging at post correlation level. For example, the Low Frequency Array (LOFAR) provides a powerful postcorrelation RFI classification tool based on combinatorial thresholding (Offringa et al., 2010a).
Generally, postcorrelation processing approaches are based on iterative algorithms including sorting and hierarchical/scaling strategies (Offringa et al., 2010b, 2012; Floer et al., 2010; Fridman, 2010). Figure 1 shows our implementation into a FPGA board of a median filter on highresolution power spectrum observations at the Nançay decameter array radio telescope. However, the high datarate at the precorrelation stages does not allow efficient implementations of these approaches due to their computational complexities.
In phased array radio telescopes, precorrelation samples are labelled with parameters such as time, frequency, polarisation, steering direction, antenna or station number. For example, phased arraybased interferometers, these samples are called beamlets. No continuity in frequency or steering direction is guaranteed between beamlets (i.e. two consecutive beamlets can represent completely different frequencies and steering directions).
In the proposed approach, each beamlet will be, independently and simultaneously, processed at different data processing stages. Therefore, the hierarchical/scaling strategy will still be possible from the antenna up to the correlator through all of the filter banks and beamformers which are implemented in between. The different detectors can be activated or not according to the RFI context of the observation. Thus, local RFI will be best detected at affected remote stations before correlating their signals with other stations, while broadband RFI will be better detected at an early stage in the channelisation process, and so on… In this way, the detectors are applied at stages where different timefrequencyspace RFI parameters can be naturally achieved and where the interferencetonoise ratio is maximum (see Figure 2), right before any dilution of RFI characteristics by subsequent channelizations or signal recombinations. Figure 3 gives an overview of the proposed approach.
These detection flags can be used in different ways:

as metadata uploaded in a specific RFI database. The latter could be used to analyse, a posteriori, the data quality and consequently the observation quality.

as flags for local RFI mitigation, such as triggering some spatial nulling a station level.

as a global flag which will be propagated up to the correlator stage. These global flags would be used to selectively integrate the corresponding data (oriented accumulation). Then, several sets of visibilities or covariance matrices with various expected quality levels will be provided and no data will be lost. According to the type of observations, these datasets could be merged or not for further processing (calibration, imaging).
To experiment with all these concepts, an ongoing case study has been conducted on the Electronic MultiBeam Radio Astronomy Concept (EMBRACE) radio telescope facility at Nançay Observatory (see Figure 4.a and (Torchinsky et al., 2016)). The objective of the experiment is to evaluate the RFI mitigation strategy in terms of hardware complexity, detection efficiency and additional RFI metadata datarate cost.
All the precorrelation processing is implemented into the UniBoard (see Figure 4.b and (Szomoru, 2010; Hargreaves, 2012)) , a generic highperformance computing platform based on Field Programmable Gate Arrays (FPGA). This board, developed under a Joint Research Activity in the RadioNet FP7 European programme is based on eight FPGA interconnected by a high speed transceiver mesh. It provides up to 4 TMACs, with ®Altera Stratix IV FPGA, and 160 Gbps data rate for the input data stream.
In Section 2 the principles of the precorrelation power detection is presented. In order to validate the concept, some simulations and a first implementation are also described. In section 3, the detailed implementation of the EMBRACEUniBoard experiment is described. Finally, conclusions and perspectives are given in section 4.
2 RFI detection criterion theoretical description
Let us define, , the digital signal at a given stage in the radio telescope data stream, is the index representing the set of parameters (e.g. channel frequency, beam number, antenna number, station number, polarisation type…). The problem is formulated as a classical binary hypothesis test where the two simple hypothesis ’ : the SignalofInterest (SOI) alone’ and ’ : SOI plus RFI’ are confronted:
(1)  
(2) 
where is a independent and identically distributed. normalized (i.e. centred and with unit variance) Gaussian complex valued random process and is a i.i.d unknown complex valued RFI with unit power. The ratio defines the interferencetonoise ratio (INR). We assume herein that and are independent.
One way to solve this problem is to use the classical approach pioneered by Neyman and Pearson which maximizes the detection probability (=Proba(reject is true) while keeping the false alarm probability (=Proba(reject is true) fixed at a constant, preferably low, value .
In general, the optimal solution can be reduced to the comparison of a criterion to a constant threshold . Under Gaussian hypothesis, the criterion would be:
(3) 
with the threshold, , defined by
(4) 
where represents the tail probability of a distribution with degrees of freedom. It has a closedform expression (Trees, 1968). For notation simplification, will be defined as , the threshold scaling factor.
However, in a realistic radio telescope environment, the power is not precisely known and that value fluctuates over time due to changes in the observational conditions (e.g. antenna position, ionospheric conditions, frequency channel properties…). Thus, in order to maintain a constant , the threshold value must be continuously updated based on adaptive estimation of and this estimation has to be robust against samples that belong to .
Ravier & DumezViou (2005) and Fridman (2008) have proposed several robust estimators of the power. Their performances are interesting but their implementations involve sorting and iterative loops which is not suitable in our ’onthefly’ operational context. In the next subsection, a robust recursive power (RRP) estimator is presented.
2.1 The robust recursive power estimator
Let us define, , the instantaneous power of the signal under test (i.e. ). Under the hypothesis, the probability density function (pdf) of is given by:
(5) 
with .
If we just consider the power amplitudes, , below , the clipped probability density function becomes:
(6) 
with .
From, the previous equation, the mean, , of these clipped power amplitudes, , is easily derived:
(7) 
Thus, the threshold can be redefined as:
(8) 
where is the correction gain to apply to to retrieve and is the truncated threshold scaling factor. Table 1 provides tabulated values of these parameters. It is interesting to notice that:
and  (9)  
and  (10) 
% clipped  

0.01  200.334  2.003  100.501  99.00 
0.1  20.339  2.034  10.508  90.48 
1  2.392  2.392  1.582  36.79 
1.5  1.757  2.635  1.287  22.31 
2  1.456  2.911  1.157  13.53 
2.5  1.288  3.220  1.089  8.21 
3  1.187  3.560  1.052  4.98 
3.5  1.122  3.928  1.031  3.02 
3.59352  1.113  4.000  1.028  2.75 
4  1.081  4.323  1.019  1.83 
4.5  1.053  4.740  1.011  1.1 
5  1.035  5.176  1.007  0.67 
7.9785  1.003  8  1.000  0.03 
In this paper, we proposed to estimate by applying a lowpass Infinite Impulse Response (IIR) filter which is only activated when the power amplitude is below the running threshold :
(11) 
where is the robust estimation of at time , () is the forgetting factor which drives the time response of the estimator. This estimator must be initialized with (e.g. or the maximum value used for computation).
The following property is easily checked under stationary hypothesis:
(12) 
Figure 5 provides an illustration of the previous equations. It shows also the robustness against RFI. Under hypothesis, this recursive variance estimator will mitigate the outliers influence and provide a robust estimation of the expected power under the hypothesis. In the next sections, some operational properties of our IIR filter are derived.
2.1.1 The equivalent estimation window length
Instead of the IIR defined in Eq. 2.1, a simple low pass Finite Impulse Response (FIR) filter could have been used:
(13) 
Since its implementation needs more memory resources, the IIR implementation has been preferred but it would be interesting to evaluate an equivalent window length for the IIR approach as a function of the forgetting factor .
For this purpose, the variance of both approaches will be compared, assuming first that is replaced by in Eq. 2.1 (i.e. clipped samples are discarded).
Thus, the variance of , is given by
(14) 
with
By matching this variance with the one obtained from Eq. 2.1.1, the equivalent estimation window length is defined by:
(15) 
which becomes when . Figure 5.b provides an illustration of this result.
To get the true equivalent estimation window length, , we have just to take into account the number of samples which freeze the estimator. In other words, has to be multiplied by the freeze factor:
(16) 
For example, let us consider a SOI stationary time interval of 1 s. Assuming 200 kHz bandwidth for the beamlet as in the EMBRACE case, the reference power should be estimated over samples, which gives nonclipped samples with according to Table 1 and finally for the robust estimator defined by Equ. 2.1.
2.1.2 The synchronisation delay
Due to the IIR filter latency, the input data has to be resynchronized with the RRP estimator.
Assuming slow variations of the reference power and by taking into account, , the freeze factor, the filter latency, , can be derived from the phase response of the IIR filter (see appendix):
(17) 
2.2 The Bernoulli power detector
As already mentioned, realtime requirements constrain the complexity of RFI detection schemes. Constraints include : limitation of resources usage, data flow continuity, and data synchronization continuity.
In this context, we propose the following approach (see Figure 6): a given window made of samples is flagged as polluted when the number of outliers, defined as , exceeds a threshold . The strategy is to implement large power threshold , short time window and to choose for strong RFI, but to implement smaller power threshold , longer time window and to choose for weak RFI. Of course, any intermediate configuration can be set up as well. All these detectors will run simultaneously and individual flags will be merged into a final flag after resynchronisation.
Let us define the probability to have . With Eq. 2.1, we get which gives where follows Eq. 2. Then, the probability to have at least samples over above is a Bernoulli distribution given by:
(18) 
where is the sum of the binary flags shiftregister content, , is the beta function, and is the incomplete beta function.
With this equation, we can compute the expected detector false alarm probability according to the parameters , and . In practice, we will have access to via the RRP estimator, thus the truncated threshold scaling factor will be preferably implemented. In the same way as for Eq.2.1, we get:
(19) 
where is the scaling threshold factor used for the RRP estimator. Table 2 provides tabulated values of these parameters for .
For the following case, , the corresponding false alarm probability simplifies to .
0.01  0.011  99.00 

0.1  0.111  90.48 
0.81415  44.30  
1  1.113  36.79 
1.5  1.670  22.31 
2  2.226  13.53 
2.5  2.783  8.21 
3  3.339  4.98 
3.5  3.896  3.02 
3.59352  4  2.75 
4  4.452  1.83 
4.5  5.009  1.1 
5  5.566  0.67 
7.187  8  0.03 
A simulation with two Bernoulli power detectors has been set up using the following parameters:

RRP estimator: and .

weak Bernoulli power detector: , samples and samples.

strong Bernoulli power detector: , samples and samples.
A white noise affected by intermittent RFI pulses with decreasing INR has been generated. Figure 7 shows the detection performance with the previous parameters. The strong pulse detector and the weak pulse one succeed in detecting pulses with INR values lower than 6 dB and 2 dB respectively. A comparison between the detector probability of false alarm in theory and evaluated after simulation is provided in Table 3.
2.3 First real time experiment
An 1channel implementation (i.e. K=1) of this detection scheme has been conducted at the Nançay Observatory (Aitallal et al., 2010). It was designed for real time radar blanking at the Nançay Decimeter Radio Telescope (NRT). Radar pulses are often an issue in radio astronomical observations. (Niamsuwan et al., 2005) has proposed some simple pulse detectors but with basic performances and (Dong et al., 2005) has defined a much more advanced algorithm that gives better performances for its finest setting. However, it includes a lot of information about the specific radar pulse shape. Any radar pulse whose shape differs significantly from the model will not be detected as easily. In our approach, radar pulse time characteristics will be used to define and .
Thus, with the same parameters as the previous simulation, the RRP estimator associated with two Bernoulli power detectors has been implemented into a VirtexII ®Xilinx FPGA. Less than 3% of the FPGA resources were used. The resulting RFI flag was used to blank 2048bins Fast Fourier Transform blocks in the final spectrometer integration leading to a final of 4.0% and 6.4% for the weak and strong pulse detector, respectively.
Figure 8 illustrates the effectiveness of this approach on real observations in the presence of radar interference. The observed bandwidth was 14 MHz wide.
In the next section, we present the ongoing implementation of all these detectors and the RRP estimator in the Uniboard. They are used to continuously monitor the data quality at different stages of a 64bins spectrometer analysing 248 complex 200 KHz beamlets generated by the EMBRACE radio telescope. The objective is to test both the relevance of an integrated RFI database and the concept of an oriented accumulation.
3 EMBRACE and UniBoard Experiment
3.1 Overview
EMBRACE is a phasedarray radio telescope (Torchinsky et al., 2016). Based on a LOFAR station firmware, it provides a set of 200 kHz digital single polarization waveforms from 2 independent beams. In our application, 248 waveforms are used as data input for Uniboard. Besides, EMBRACE by itself provides some regular statistics as well (100 MHz bandwidth power statistics for all analog inputs and 200 kHz correlation statistics) on the received data. These statistics will be added in the RFI monitoring system as well, but it is outside of the scope of this paper.
In radio astronomy, the elementary timefrequency slot shape is driven by radio telescope design considerations, basically from wide bandwidth in the front end to narrow bandwidth in the backend (see Figure 3). In our experiment, we have set up a similar scheme but at a smaller scale.
Thus, UniBoard has been configured for two main tasks (see Figure 9). The first one is the data quality monitoring of these beamlets at different timefrequency resolutions (200 kHz, 200/8 kHz and 200/64 kHz). For this purpose, each beamlet is decomposed into 64 channels with two successive 8bin polyphase filter banks (PFB). These PFB are maximally decimated (i.e. the output rate is the input rate divided by 8). At each stage, a detection module monitors the data and provides RFI information about data quality. This information, named RFIlet, is sent to the RFI database. The proposed multiresolution approach is a way to improve the scaling between detector timefrequency resolution and RFI characteristics. For example, assuming white noise and a narrow band interferer, the interference to noise ratio (INR) will be 18 dB better at the output than at the input.
The second one consists in delivering of 64bins power spectral estimators for all the 200 kHz input beamlets. The spectrum accumulation is driven in real time by the previous data quality analysis. This approach is called oriented accumulation. Clean data and flagged data are accumulated separately. In the current implementation, the RFI flagging is binary but a multilevel decision could be easily implemented as well. Consequently, no data are lost and the enduser has the option to use or not the flagged data. The RFI decision process is based on inheritance: once a sample from a given channel is detected as polluted, all subchannels linked with this sample are flagged as well. It is a rather conservative approach but according to the RFI context other rules could be implemented.
3.2 UniBoard Detection module firmware
Figure 10 gives an overview of an RFI detection module. It includes:

a flagging module: each detector analyzes a set of consecutive time samples from a given channel and triggers a flag if the threshold is reached. The analysis window lengths, , and the thresholds, and , are static parameters. In the current implementation, the detectors are based on the Bernoulli power detector scheme (see Figure 12). All these detectors are calibrated by the RRP estimator (see Figure 11).

a synchronization module: Each detector generates its own latency (mainly parametrized by ). Consequently, all RFI flags and waveforms must be synchronized with the longest latency. This is one of the tricky parts of the design and it is very technical. Therefore, we do not provide a detailed analysis of this module. The RFI flags provided by the Bernoulli power detector modules flag only the last sample of their respective detection windows. The purpose of this synchronization module is to expand the flags all over the detection windows and then to merge all these signals into one final RFI flag. A simple OR function is used in this version but more complex rules could be implemented. This module is connected with the RFIlet generator which communicates with the RFI database.

A blanking module: 3 modes are available (part of the static configuration):

Gothrough mode: waveform time samples are flagged, the waveforms are not modified.

Zero mode: flagged waveform time samples are replaced by zeros

Gaussian mode: flagged waveform time samples are replaced by synthesized complex Gaussian samples of the same variance (not implemented in the current firmware version).

For the Uniboard RRP estimator implementation, Eq. 2.1 has been reordered in the following way:
(20) 
where so that the corresponding multiplier can be implemented as a simple bitshift with no resource cost. Thus, for , the equivalent estimation window length, . is a static parameter.
With the same considerations, it could be convenient to choose the static threshold scaling factor as a power of 2. According to Table 1, two values are valid, or , which gives a percentage of clipped samples equal to 2.75% and 0.03%, respectively.
Figure 11 shows the detailed design. A valid signal is attached to the waveform data and is used to freeze the design when no valid data is available at the input. All data are time stamped to keep track of the data stream integrity. All this information is put into a serial data bus which is compliant with the Altera Avalon standard (Altera, 2015). To speed up the design, it is possible to insert registers between the operators. This will modify the IIR filter response but assuming slow variations of , all the previous study will be still valid. With similar considerations, it is also possible to remove the IIR resynchronization module. This module is based on Eq. 2.1.2.
The synthesis report indicates a maximum clock frequency of 250 MHz (we need 180 MHz). The amount of multipliers is low, especially if powerof2 scaling factors are set up. The memory requirement is high since it depends on , the number of channels. However it is manageable especially if we consider slow variations of so that we can remove the IIR resynchronization module.
4 Conclusions and perpectives
SKA will be built in a quiet zone far from inhabited areas, except perhaps for some remote stations. SKA will have to face intermittent interference from satellite systems and airplanes. These signals are relatively strong.
Our approach is based on multiscale elementary timefrequency slot shapes driven by radio telescope design considerations. Furthermore, for optimal RFI detection performances, timefrequency slots should be adapted to RFI timefrequency shapes. In this case, the INR is maximized and all the RFI timefrequency characteristics, which can be used for detection, are preserved. We have proposed a lowcost power detection scheme which can be implemented in the precorrelation stages at different levels from large bandwidth in the frontend to narrow bandwidth in the backend. This RFI monitoring system can be used to feed an RFI database and/or trigger for other more complex RFI mitigation techniques. Thus, the digital signal processing resources could be fully dedicated to regular signal processing tasks most of the time and could be partially reused (scheduled) for observations facing specific RFI issues and requiring specific RFI mitigation techniques.
A first FPGA implementation designed for a specific timefrequency resolution level has proved the effectiveness of the proposed power detection scheme. Our RRP estimator provides a robust and adaptive estimation of the reference power even in presence of intermittent RFI, and our Bernoulli power detector can achieve low INR RFI detection at a very low implementation cost.
A second implementation based on a high performance computing board, UniBoard, has been described. The objective is to generate a multilevel detection scenario based on data received by the EMBRACE radio telescope. At each level, our power detection scheme is implemented and the resulting RFI flags are used to drive the final spectrum integration and to feed an RFI database. This experiment is still in progress.
The power based detectors are widely implemented in practice since no RFI a priori information is used. However, to improve the detection performances, we plan to implement more specific detectors based on adhoc RFI characteristics such as non Gaussianity (Nita et al., 2007), spectral properties (Hellbourg et al., 2012), cyclostationary properties (Weber et al., 2007). As these implementations will used more resources, a new generation UniBoard will be targeted. This Uniboard2 (see Figure 13), also developed under a Joint Research Activity in the RadioNet3 FP7 European programme, is based on 4 ®Altera Arria 10. It provides up to 3.6 TMACs and 2 Tbps into front side generic interfaces.
Acknowledgments
The authors would like to thank the European Commission Framework Program 7 ( Project Radionet Uniboard, contract no 227290 and project Radionet Uniboard2, contract no 283393) for funding this research on RFI mitigation and its hardware implementation.
Appendix : The synchronisation delay
The transfer function of the IIR filter defined in Eq. 2.1 is given by:
(21) 
Thus, the frequency response is given by:
(22) 
From the previous equation, the phase response can be derived :
(23) 
Assuming slow variations of the reference power (i.e. ), we get the following approximation
(24) 
From the previous equation, the response time delay can be derived:
(25) 
By taking into account the frozen samples (see Eq. 2.1.1), the true delay is given by:
(26) 
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