Memcomputing NP-complete problems in polynomial time using polynomial resources and collective states

Memcomputing NP-complete problems in polynomial time using polynomial resources and collective states

Fabio L. Traversa fabio.traversa@polito.it Department of Physics, University of California, San Diego, La Jolla, California 92093, USA Department of Electronics and Telecommunications, Politecnico di Torino, Turin, Italy    Chiara Ramella chiara.ramella@polito.it Department of Electronics and Telecommunications, Politecnico di Torino, Turin, Italy    Fabrizio Bonani fabrizio.bonani@polito.it Department of Electronics and Telecommunications, Politecnico di Torino, Turin, Italy    Massimiliano Di Ventra diventra@physics.ucsd.edu Department of Physics, University of California, San Diego, La Jolla, California 92093, USA
July 14, 2019
Abstract

Memcomputing is a novel non-Turing paradigm of computation that uses interacting memory cells (memprocessors for short) to store and process information on the same physical platform13_memcomputing (). It was recently proved mathematically that memcomputing machines have the same computational power of non-deterministic Turing machinestraversa_UMM (). Therefore, they can solve NP-complete problems in polynomial time and, using the appropriate architecture, with resources that only grow polynomially with the input size. The reason for this computational power stems from properties inspired by the brain and shared by any universal memcomputing machine, in particular intrinsic parallelism and information overheadtraversa_UMM (), namely the capability of compressing information in the collective state of the memprocessor network. Here, we show an experimental demonstration of an actual memcomputing architecture that solves the NP-complete version of the subset-sum problem in only one step and is composed of a number of memprocessors that scales linearly with the size of the problem. We have fabricated this architecture using standard microelectronic technology so that it can be easily realized in any laboratory setting. Even though the particular machine presented here is eventually limited by noise–and will thus require error-correcting codes to scale to an arbitrary number of memprocessors–it represents the first proof-of-concept of a machine capable of working with the collective state of interacting memory cells, unlike the present-day single-state machines built using the von Neumann architecture.

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I Introduction

There are several classes of computational problems that require time and resources that grow exponentially with the input size when solved. This is true when these problems are solved with deterministic Turing machines, namely machines based on the well-known Turing paradigm of computation which is at the heart of any computer we use nowadays complexity_bible (); computer_architecture_book (). Prototypical examples of these difficult problems are those belonging to the class that can be solved in polynomial (P) time if a hypothetical Turing machine–named non-deterministic Turing machine–could be built. They are classified as non-deterministic polynomial (NP) problems, and the machine is hypothetical because, unlike a deterministic Turing machine, it requires a fictitious “oracle” that chooses which path the machine needs to follow to get to an appropriate state 36_turing (); turing_book (); complexity_bible (). As of today, no one knows whether NP problems can be solved in polynomial time by a deterministic Turing machine computational_complexity_book (); NP_optical (). If that were the case we could finally provide an answer to the most outstanding question in computer science, namely whether NPP or notcomplexity_bible ().

Very recently a new paradigm, named memcomputing 13_memcomputing () has been advanced. It is based on the brain-like notion that one can process and store information within the same units (memprocessors) by means of their mutual interactions. This paradigm has its mathematical foundations on an ideal machine, alternative to the Turing one, that was formally introduced by two of us (FT and MD) and dubbed universal memcomputing machine (UMM) traversa_UMM (). Most importantly, it has been proved mathematically that UMMs have the same computational power of a non-deterministic Turing machine traversa_UMM (), but unlike the latter, UMMs are fully deterministic machines and, as such, they can actually be fabricated. A UMM owes its computational power to three main properties: intrinsic parallelism–interacting memory cells simultaneously and collectively change their states when performing computation; functional polymorphism–depending on the applied signals, the same interacting memory cells can calculate different functions; and finally information overhead–a group of interacting memory cells can store a quantity of information which is not simply proportional to the number of memory cells itself.

These properties ultimately derive from a different type of architecture: the topology of memcomputing machines is defined by a network of interacting memory cells (memprocessors), and the dynamics of this network are described by a collective state that can be used to store and process information simultaneously. This collective state is reminiscent of the collective (entangled) state of many qubits in quantum computation, where the entangled state is used to solve efficiently certain types of problems such as factorization QI_bible (). Here, we prove experimentally that such collective states can also be implemented in classical systems by fabricating appropriate networks of memprocessors, thus creating either linear or non-linear combinations out of the states of each memprocessor. The result is the first proof-of-concept machine able to solve an NP-complete problem in polynomial time using collective states.

The experimental realization of the memcomputing machine presented here, and theoretically proposed in Ref. traversa_UMM (), can solve the NP-complete Karp_10 () version of the subset-sum problem (SSP) in polynomial time with polynomial resources. This problem is as follows: if we consider a finite set of cardinality , is there a non-empty subset whose sum is a given integer number ? As we discuss in the following paragraphs, the machine we built is analog and hence would be scalable to very large numbers of memprocessors only in the absence of noise or using some error-correcting codes. This problem derives from the fact that in the present realization we use the frequencies of the collective state to encode information and, to maintain the energy of the system bounded, the amplitudes of the frequencies are dampened exponentially with the number of memprocessors involved. However, this latter limitation is due to the particular choice of encoding the information in the collective state, and could be overcome by employing other realizations of memcomputing machines that are digital and using error-correcting codes. For example in Ref. traversa_UMM () two of us (FT and MD) proposed a different way to encode a quadratic information overhead in a network of memristors that is not subject to this energy bound.

Another example in which information overhead does not need exponential growth of energy is again quantum computing. For instance, a close analysis of the Shor’s algorithm Shor_1 () shows that the collective state of the machine implements all at once (through the superposition of quantum states) an exponential number of states, each one with the same probability that decreases exponentially with the number of qubits involved. Successively, the quantum Fourier transform reorganizes the probabilities encoded in the collective state and “selects” those that actually solve the implemented problem (the prime factorization in the case of the Shor’s algorithm). It is worth noticing, however, that also quantum computing algorithms necessarily require error-correcting codes for their practical implementation due to the several unavoidable sources of noise QI_bible ().

Here, it is also worth stressing that our results do not answer the NPP question, since the latter has its solution only within the Turing-machine paradigm: although a UMM is Turing-complete traversa_UMM (), it is not a Turing machine. In fact, (classical) Turing machines employ states of single memory cells and do not use collective states. Finally, we mention that other unconventional approaches to the solution of NP-complete problems have been proposed NP_optical (); NP_optical2 (); NP_quantum (); NP_molecular (); NP_DNA (); NP_light (), however none of them reduces the computational complexity or requires physical resources not exponentially growing with the size of the problem. On the contrary, our machine can solve an NP-complete problem with only polynomial resources. As anticipated, this last claim is strictly valid for an arbitrary large input size only in the absence of noise.

Ii Results

ii.1 Implementing the SSP.

Figure 1: Scheme of the memcomputing architecture used in this work to solve the subset-sum problem. The central spectrum has been obtained by the discrete Fourier transform of the experimental output of a network of 6 memprocessors encoding the set with fundamental frequency  Hz.
Figure 2: (a) Simplified schematic of the memprocessor architecture used in this work to solve the subset-sum problem (more details can be found in the Supplementary Information). (b) Schematic of the frequency shift module.

The machine we built to solve the SSP is a particular realization of a UMM based on the memcomputing architecture described in Ref. traversa_UMM (), namely it is composed of a control unit, a network of memprocessors (computational memory) and a read-out unit as schematically depicted in Figure 1. The control unit is composed of generators applied to each memprocessor. The memprocessor itself is an electronic module fabricated from standard electronic devices, as sketched in Figure 2 and detailed in the Materials and Methods section. Finally, the read-out unit is composed of a frequency shift module and two multimeters. All the components we have used employ commercial electronic devices.

The control unit feeds the memprocessor network with sinusoidal signals (that represent the input signal of the network) as in Figure 1. It is simple to show that the collective state of the memprocessor network of this machine (that can be read at the final terminals of the network) is given by the real (up terminal) and imaginary (down terminal) part of the function

(1)

where is the number of memprocessors in the network and the imaginary unit (see Materials and Methods or Ref. traversa_UMM ()). If we indicate with the -th element (integer with sign) of , and we set the frequencies as with the fundamental frequency equal for any memprocessor, we are actually encoding the elements of into the memprocessors through the control-unit feeding frequencies. Therefore, the frequency spectrum of the collective state (1) (or more precisely the spectrum of ) will have the harmonic amplitude, associated with the normalized frequency , proportional to the number of subsets whose sum is equal to . In other words, if we read the spectrum of the collective state (1), the harmonic amplitudes are the solution of the subset sum problem for any . From this first analysis we can make the following considerations.

Information overhead: the memprocessor network is fed by frequencies encoding the elements of , but the collective state (1) encodes all possible sums of subsets of into its spectrum. It is well known computational_complexity_book () that the number of possible sums (or equivalently the scaled frequencies of the spectrum) can be estimated in the worst case as where . Obviously (sometimes called the capacity of the problem) has exponential growth algorithms_book () on the minimum number of bits used to represent the elements of ( is called precision of the problem and we have , if we take the precision in bits). Thus the spectrum of the collective state (1) encodes an information overhead that grows exponentially with the precision of the problem.

Computation time: the collective state (1) is a periodic function of with minimum period because all frequencies involved in (1) are multiples of the fundamental frequency . Therefore, is the minimum time required for computing the solution of the SSP within the memprocessor network and so it can be interpreted as the computation time of the machine. However, this computation time is independent of both and .

Energy expenditure: the energy required to compute the SSP can be estimated as that quantity proportional to the energy of the collective state in one period . By using (1) we have , so also the energy needed for the computation is independent of both and . It is worth remarking here that, in order to keep the energy bounded, all generators have the coefficient 0.5 (see Figure 1) then introducing (see Materials and Methods) the factor in Eq. (1). This means that all frequencies involved in the collective state (1) are dampened by the factor . In the case of the ideal machine, i.e., a noiseless machine, this would not represent an issue because no information is lost. On the contrary, when noise is accounted for, the exponential factor represents the hardest limitation of the experimentally fabricated machine, which we reiterate is a technological limit for this particular realization of a memcomputing machine but not for all of them.

ii.2 Reading the SSP solution

With this analysis we have proven that the UMM represented in Figure 1 can solve the SSP with memprocessors, a control unit formed by generators and taking a time and an energy independent of both and . Therefore, at first glance, it seems that this machine (without the read-out unit) can solve the SSP using only resources polynomial (specifically, linear) in . However, we need one more step: we have to read the result of the computation. Unfortunately, we cannot simply read the collective state (1) using, e.g., an oscilloscope and performing the Fourier conversion. This is because the most optimized algorithm to do this (see Materials and Methods and Ref. traversa_UMM ()) is exponential in , i.e., it has the same complexity of standard dynamic programming algorithms_book ().

However, a solution to this problem can be found by just using standard electronics to implement a read-out unit capable of extracting the desired frequency amplitude without adding any computational burden. In Figure 1 we sketch the read-out unit we have used. It is composed of a frequency-shift module and two multimeters. The frequency shift module is in turn composed of two voltage multipliers and two sinusoidal generators as depicted in Figure 2 and it works as follows. If we connect to one multiplier the real part of a complex signal and to the other multiplier the imaginary part, we obtain at the outputs and . The sum and difference of the two outputs are and . From basic Fourier calculus, and are the frequency spectrum shifts of and for the function , respectively. Consequently, if we read the DC voltages and of and using two multimeters and perform the sum and difference we obtain the amplitudes and of the harmonics at the frequencies and , respectively (see Figure 1).

Hence, by feeding the frequency shift module with the and from (1), reading the output with the two multimeters, and performing sum and difference of the final outputs we obtain the harmonic amplitude for a particular normalized frequency according to the external frequency of the frequency-shift module. In other words, without adding any additional computational burden and time, we can solve the SSP for a given by properly setting the external frequency of the frequency-shift module.

It is worth noticing that, if we wanted to simulate our machine by including the read-out unit the computational complexity would be (close to the standard dynamic programming that is algorithms_book ()). In fact, from the Nyquist-Shannon sampling theoremwiley_enc (), the minimum number of samples of the shifted collective state (i.e,. the outputs of the frequency-shift module) must be equal to the number of frequencies of the signal (in our case of ) in order to accurately evaluate even one of the harmonic amplitudes Goertzel (). The last claim can be intuitively seen from this consideration: the DC voltage must be calculated in the simulation by evaluating the integral and this requires at least samples for an accurate evaluation wiley_enc (). On the other hand, the multimeter of the hardware implementation, being essentially a narrow low-pass filter, performs an analog implementation of the integral over a continuous time interval (independent of and ), directly providing the result, thus avoiding the need of sampling the waveform and computing the integral.

Figure 3: Spectra of internal collective state of three different networks with fundamental frequency  Hz. 4–memprocessor network encodes the set . 5–memprocessor network encodes . 6–memprocessor network encodes .
#subs. #subs.
[KHz] [mV] [mV] [V] [V] sum sum
0 0 31.7 0 1.02 1.02 1 1
74 7.4 15.3 15.0 1.94 0.02 2 0
130 13.0 -0.2 14.9 0.94 -0.97 1 1
146 14.6 14.8 15.8 -0.06 1.96 0 2
248 24.8 7.6 7.2 0.95 0.02 1 0
485 48.5 -0.4 -0.7 -0.07 0.02 0 0
486 48.6 -8.9 6.6 -0.14 0.99 0 1
Table 1: Measurements from the read-out unit of Figure 1 for a 6–memprocessor network with fundamental frequency  Hz encoding the set . In the fifth and sixth columns the voltages are respectively given by and . The last two columns are the analytical results.

In Figure 3 the absolute value of the spectrum of the collective state for networks of 4, 5 and 6 memprocessors is compared with the theoretical results given by the spectrum of (1) (see Materials and Methods for more details on the hardware and measurement process). Non-idealities of the circuit and electronic noise in general are the sources of the small discrepancies with respect to the theoretical results. Nevertheless, the machine we fabricated demonstrates that using the collective state of all memprocessors, instead of the uncoupled states of the individual memory units, we can carry out difficult computing tasks (NP-complete problems) with polynomial resources. Finally, in Table 1, the measurements at the read-out circuit are listed for different harmonics for a 6-memprocessor network. The precision is up the third digit as can be seen from the comparison with the theoretical results.

Iii Discussion

iii.1 Scalability and Error Correction

As anticipated, the machine we have built would ultimately be limited by unavoidable noise sources, thus requiring error-correcting codes. However we prove here that under the assumption of low noise, additive white noise does not affect the machine output. Therefore, only non-idealities of the devices and colored noise represent a limit for this particular machine. To analyze this issue we consider first the simplest case of independent white Gaussian additive noise sources for each memprocessor. Under this hypothesis each memprocessor has complex noisy input of the form . When we connect two memprocessors, the output at the terminals of the second memprocessor is given by

(2)

If the noise term is small enough (low noise components) the quantity is negligible compared to the other terms and can be neglected. Following the same steps, the network composed of memprocessors has collective state (under low noise condition) of the form

(3)

Using the expression (3) we can calculate the signal-to-noise-ratio as the ratio between the power of the signal and the power of the noise. The signal power (neglecting noise) is simply given by and the noise power is given by , where is the expectation value operator. Since the noise sources are independent we have , and being the sources white is independent of time. Finally, assuming for any and we have and the signal-to-noise ratio reads

(4)

However, being the noise withe, the noise power spectrum, according to (3), is distributed among the different harmonics with weights given by the coefficients in (3) that are exponentially decreasing with . Therefore, the signal to noise ratio for each harmonic has the same order of magnitude of (4) and hence the withe noise (under conditions of low noise) does not affect the machine when we scale it up.

On the other hand, non-idealities, colored and noise and other non-Gaussian noise sources, have spectra that are not distributed on the harmonics as withe noise. For example, the noise accumulates on the output harmonic during the process of measurement. Nevertheless, if the total noise can be considered low, the equation (3) is still valid but the ratio (4) should be taken frequency dependent. In this case we can apply the Shannon’s noisy-channel coding theorem Shannon () with our machine interpreted as a noisy channel with capacity . The input is given by the control unit and the output is the collective state . The Shannon theorem then states that for any and , there exists a code of length and rate and a decoding algorithm, such that the maximal probability of block error is .

In addition, using the Shannon–Hartley theorem Communication_book () we have that for frequency dependent noise the capacity can be calculated as

(5)

where is the bandwidth of the channel. In our case, the lower bound of can be taken as linear in the number of memprocessors, i.e., with a constant, and is given by (4). We finally have (for large )

(6)

where .

We therefore conclude that our machine compresses data in an exponential way with constant capacity. At the output we have the exponential decreasing probability of finding one solution of the subset sum problem when we implement brute force the algorithm, i.e., without any error-correcting coding. However, from Shannon theorem, there exists a code that allows us to send the required information with bounded error. The question is then whether there is a polynomial code that accomplishes this task. We briefly discuss here the question heuristically. If our machine were Turing-like, the polynomial code could exist only if . Instead, our machine is not Turing-like, and the channel can perform an exponential number of operations at the same time. Since this is similar to what quantum computing does when solving difficult problems such as factorization, and we know that for quantum computing polynomial correcting codes do exist QI_bible (), we expect similar coding can be applied to our specific machine as well.

Iv Conclusions

In summary, we have demonstrated experimentally a deterministic memcomputing machine that is able to solve an -complete problem in polynomial time (actually in one step) using only polynomial resources. The actual machine we built clearly suffers from technological limitations due to unavoidable noise that impair its scalability. These limitations derive from the fact that we encode the information directly into frequencies, and so ultimately into energy. This issue could, however, be overcome either using error correcting codes or with other UMMs that use other ways to encode such information and are digital at least in their input and output. Irrespective, this machine represents the first experimental realization of a UMM that uses the collective state of the whole memprocessor network to exploit the information overhead theoretically introduced in Ref. traversa_UMM (). Finally, it is worth mentioning that the machine we have fabricated is not a general purpose one. However, other realizations of UMMs are general purpose and can be easily built with available technologyDCRAM (); 07_waser (); 08_strukov (); 09_memory_materials (); 12_grollier (). Their practical realization would thus be a powerful alternative to current Turing-like machines.

V Materials and Methods

v.1 Experimental Design

The operating frequency range of the experimental setup needs to be discussed with the measurement target in mind. For the measurement of the entire collective state, the limiting frequency is due to the oscilloscope we use to sample the full signal at the output of the memprocessor network. On the other hand, the measurement of some isolated harmonic amplitudes using the read-out unit, transfers this bottleneck to the voltage generators and internal memprocessor components. It is worth stressing that measuring the collective state is not the actual target of our work because it has the same complexity of the standard algorithms for the SSP as discussed in the Results section and in Ref. traversa_UMM (). Here, for completeness, we provide measurements of the collective state only to prove that the setup works properly. The actual frequency range of the setup is discussed in the next section.

v.2 Setup frequency range

Let us consider , and the integer

(7)

We also consider and we encode the in the frequencies by setting the generators at frequencies , so the maximum frequency of the collective state is . From these considerations, we can first determine the range of the voltage generators: it must allow for the minimum frequency (resolution)

(8)

and maximum frequency (bandwidth)

(9)

We employed the Agilent 33220A Waveform Generator111Note that when we use digital voltage generators we need to control the frequency with precision proportional to . Therefore, generating waveforms with digital generators should require exponential resources in because of the time sampling. However, this can be in principle overcome using synchronized analog generators designed for this specific task., which has 1 Hz resolution and 20 MHz bandwidth. This means that, in principle, we can accurately encode when composed of integers with a precision up to 13 digits (which is quite the same precision of the standard double-precision integers) provided that a stable and accurate external clock reference, such as a rubidium frequency standard is used. This is because the internal reference of such generators introduces a relative uncertainty on the synthesized frequency in the range of some parts-per-billion () thus limiting the resolution at high frequency, down to few mHz at the maximum frequency. However, as anticipated, this issue can be resolved by employing an external reference providing higher accuracies. On the other hand, note that the frequency range can be, in principle, increased by using wider bandwidth generators, up to the GHz range.

Another frequency limitation concerning the maximum operating frequency is given by the electronic components of the memprocessors. In fact, the active elements necessary to implement in hardware the memprocessor modules have specific operating frequencies that cannot be exceeded. Discrete operational amplifiers (OP-AMPs) are the best candidates for this implementation due to their flexibility in realizing different types of operations (amplification, sum, difference, multiplication, derivative, etc.). Their maximum operating frequency is related to the gain-bandwidth product (GBWP). We used standard high frequency OP-AMP that can reach GBWP up to few GHz. However, such amplifiers usually show high sensitivity to parasitic capacitances and stability issues (e.g., a limited stable gain range). Typical maximum bandwidth of such OP-AMPs that ensures unity gain stability and acceptable insensitivity to parasitics are of the order of few tens of MHz, thus compatible with the bandwidth of the Agilent 33220A Waveform Generator. Therefore, we can set quantitatively the last frequency limit related to the hardware as

(10)

and ensure optimal OP-AMP functionality. Finally using (8)-(10) we can find a reasonable satisfying the frequency constraints.

v.3 Memprocessor

The memprocessor, synthetically discussed in the Results section and sketched in Figure 2, is shown in the pictures of Figure S1-(a) and a more detailed circuit schematics is given in Figure S1-(b). Each module has been realized as a single Printed Circuit Board (PCB) and connections are performed through coaxial cables with BNC terminations. According to Figure 2, each memprocessor must perform one derivative , four multiplications, one sum and one difference. Since and , then , i.e. the quadrature signal with respect to the input . This can be easily obtained with the simple OP-AMP-based inverting differentiator depicted in Figure S1-(b), designed to have unitary gain at frequency . Similarly, an inverting summing amplifier and a difference amplifier can be realized as sketched in Figure S1-(b) to perform sum and difference of voltage signals, respectively. The OP-AMP selected is the Texas Instruments LM7171 Voltage Feedback Amplifier.

Implementing multiplication is slighly more challenging. OP-AMP based analog multipliers are very sensitive circuits. Therefore, they need to be carefully calibrated. This makes a discrete OP-AMP based realization quite challenging and the integration expensive. We thus adopted a pre-assembled analog multiplier: the Texas Instrument (Burr-Brown) MPY634 Analog Multiplier, which ensures four-quadrant operation, good accuracy and wide enough bandwidth (10MHz). The only drawback of this multiplier is that the maximum precision is achieved with a gain of 0.1. Therefore, being the input signals in general quite small, this further lowering of the precision can make the output signal comparable to the offset voltages of the subsequent OP-AMP stages. For this reason, we have included in the PCB a gain stage (inverting amplifier) before each output to compensate for the previous signal inversion and lowering. These stages permit also manual offset adjustment by means of a tunable network added to the non-inverting input, as shown in the schematic. Finally a low-pass filter with corner frequency has been added to the outputs to limit noise. Figure S1-(a) shows a picture of one of the modules, which have been realized on a 100 mm 80 mm PCB. The power consumption of each module is quite high since all of the 10 active components work with V supply. OP-AMPs have a quiescent current of 6.5 mA, while the multipliers a quiescent current of 4 mA, yielding a total DC current of around 50 mA per module.

Finally, we briefly discuss how connected memprocessors work. From Figure 2, if we have , and for an arbitrary complex function , at the output of the memprocessor we will find

(11)
(12)

Since we can only set positive frequencies for the generators, in order to encode negative frequencies (i.e., a negative ) we can simply invert the input and output terminals as depicted in Figure S1-(c). Therefore, if we set for the first memprocessor, i.e., and , at the output of the first memprocessor we will find the real and imaginary parts of that will be the new for the second memprocessor. Proceeding in this way we find the collective state (1) at the end of the last memprocessor.

v.4 Analysis of the Collective State

In order to test if the memprocessor network correctly works, we have carried out the measurement of the full collective state at the end of the last memprocessor. This task requires an extra discussion on the operating frequency range. Indeed, the instrument we used to acquire the output waveform is the LeCroy WaveRunner 6030 Oscilloscope. The measurement process consists in acquiring the output waveforms and apply the FFT in software. Being the collective state a purely periodic signal, i.e., a signal containing only frequencies multiples of and with known maximum frequency , from the discrete Fourier transform theory and Nyquist-Shannon sampling theoremtraversa_UMM (); wiley_enc (), we need to sample the interval into subintervals of width to compute the exact spectrum of . In other words we need samples with and to compute the exact spectrum of . Therefore, with the oscilloscope we must be able to acquire at least samples of into the time interval .

This relationship turns out to be a constraint on the usable frequency range since we must perform the measurement in a reasonable time, and we cannot exceed the maximum sampling frequency of the instrument that we use for acquisition, nor its maximum memory capability. In our experimental proof, the LeCroy WaveRunner 6030 Oscilloscope is characterized by 350 MHz bandwidth, 2.5 GSa/s sampling rate and discretization points when saving waveforms in ascii format (i.e., ). The bandwidth of the oscilloscope is very large thus it is not really a constraint, while the limit is, in fact we have the constraint

(13)

With this value, choosing  Hz allows to have ,  KHz and requires 1 s measurement time which is a quite long time in electronics. Therefore, without varying , we can choose larger that allows for a smaller measurement time. We choose  Hz which means a measurement time of only few tens of ms, and  MHz.

v.5 Experimental set-up

The laboratory set-up we have employed is sketched in Fig. S2-(a), while Fig. S3 reports a picture of the same. The order of cascade connection of the memprocessors is arbitrary. For this test, we ordered the module such that (see Figure S2-(a)) in order to have the two memprocessors related to the two positive numbers (130 and 118) at the beginning and at the end of the chain, respectively, thus minimizing the number of the “swapped” connections (see Figure S1-(c)). A two-output power supply (model Agilent E3631A) is used to generate both the and  V at the inputs of the first memprocessor and the V supply for all the modules (parallel connection). The input of each module is generated by a Agilent 33220A waveform generator, while the output is observed through both an oscilloscope (model LeCroy Waverunner 6030, see Figure S2-(c)) and a multimeter (model Agilent 34401A). In particular, the oscilloscope is used for the AC waveform, while the multimeter mesured the DC component in order to avoid errors due to the oscilloscope probes which are very inaccurate at DC and may show DC offsets up to tens of mV.

Another issue concerns the synchronization of the generators. The six generators we use must share the same time base and they must have the same starting instant (the instant) when all the cosine waveforms must have amplitude 0.5 V. To have a common time base we used the 10 MHz time base signal of one of the generators (master) and we connected the master output signal to all the other (slave) generators at the 10 MHz input. In this way they ignore their own internal time base and lock to the external one. In order to have a common instant we must run the generators in the infinite burst mode. In this mode the generators produce no output signal until a trigger input is given, and then they run indefinitely until they are manually stopped. The trigger input can be external or manual (soft key): the master device is set up to expect a manual input while the slave devices are controlled by an external trigger coming from the master. Finally, in order to correctly visualize the output waveforms we must “synchronize” also the oscilloscope. The trigger signal of the oscilloscope must have the same frequency of the signal to be plotted, or at least one of its subharmonics. Otherwise, we see the waveform moving on the display and, in case two or more signals are acquired, we lose the information concerning their phase relation. To solve this problem we connect the external trigger input of the oscilloscope to a dedicated signal generator, producing a square waveform at frequency , which is the greatest common divisor of all the possible frequency components of the output signals. This dedicated generator is also used as the master for synchronization. Fig. S2-(b) shows how the generators must be connected in order to obtain the required synchronization.

Acknowledgements

The hardware realization of the machine presented here was supported by Politecnico di Torino through the Neural Engineering and Computation Lab initiative. MD acknowledges partial support from CMRR.

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Supplementary Information

Figure 4: Memprocessor module. (a) Pictures, (b) schematic, (c) connection rule of the memprocessor module.
Figure 5: (a) Sketch of the laboratory test bench. (b) Synchronization of the waveform generators. (c) Collective state of 6 memprocessors network read by the oscilloscope.
Figure 6: Pictures of the laboratory test bench.
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